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Lead-resistance subtraction in two-wire measurements corrects a specimen reading using a separate shorted-lead reading intended to estimate the unwanted series resistance. The correction is useful only to the extent that the lead and contact contributions remain known between the two arrangements. Keithley identifies lead resistance as an added term in the two-wire resistance measurement circuit and distinguishes it from additive thermoelectric offsets.^[ref]

An original measurement model makes the residual explicit. Let the specimen reading bewhere $R_x$ is the desired electrical resistance, $R_L$ and $R_C$ are included lead and contact resistances, and $E$ is an additive potential-difference offset. If the shorting connection has resistance $R_s$, its reading isSubtraction givesThe short is an actual electrical connection, not necessarily an exact zero. Replacing the specimen also changes contacts, so their contributions need not be identical.

For a numerical example, take $R_x=0.200\Omega$, stable total lead resistance $0.300\Omega$, negligible other contacts and offsets, and $R_s=0.005\Omega$. The specimen reading is $0.500\Omega$, the short reading $0.305\Omega$, and subtraction gives $0.195\Omega$, a $2.5\%$ negative error. If the leads subsequently rise to $0.312\Omega$, retaining that old short reading instead gives $0.207\Omega$, a $3.5\%$ positive error. Accurate arithmetic cannot establish that the two series contributions were equal.

A simple temperature model predicts one drift mechanism. If lead resistance follows $R_L(T)\simeq R_L(T_0)[1+\alpha (T-T_0)]$, then $\Delta R_L\simeq \alpha R_L\Delta T$. With stipulated $R_L=0.300\Omega$, $\alpha =0.0039{\mathrm{K}}^{-1}$ and $\Delta T=10\mathrm{K}$, the residual is $0.0117\Omega$, or $5.85\%$ of the example specimen. The actual temperature coefficient of resistance and temperature history must be established for the leads used.

Uncertainty in a difference includes covariance:This is the difference specialization of the primary uncertainty-propagation law.^[ref] With $u_t=u_0=1\mathrm{m\Omega }$ and correlation $0.9$, the difference uncertainty is about $0.447\mathrm{m\Omega }$; assuming independent readings would give $1.414\mathrm{m\Omega }$. Positive correlation can reduce a shared additive contribution, but a common gain error still scales the corrected specimen resistance.

An unchanged thermal offset also fails to cancel if the test currents differ: for $E_t=E_0=20\mu \mathrm{V}$, $I_t=10\mathrm{mA}$ and $I_0=1\mathrm{mA}$, its residual is $-0.018\Omega$. Current reversal within each arrangement can address a stable additive offset, but does not remove series resistance drift. Four-terminal sensing addresses the lead-drop geometry by measuring potential difference separately at the chosen specimen terminals.

A proposed check alternates short and specimen measurements while recording current and lead temperature, repeats after reconnecting the clips, and compares against a four-terminal result. The spread after reconnection tests a different contribution from rapid repeatability without disturbing the circuit. Report the defined specimen boundary, short construction and delay between readings rather than treating a successful zero display as a complete accuracy assessment.

A microbolometer is a miniaturized bolometer in which absorbed electromagnetic radiation heats a thermally isolated sensing element and the readout detects the resulting change in electrical resistance. Arrays of microbolometers can form an infrared image without cryogenic detector cooling. A pixel commonly has an absorbing membrane suspended above its readout circuit on narrow supports.^[ref]

An elementary small-signal heat transfer model writesHere $C$ is the sensing element's heat capacity, $G$ its thermal conductance to a fixed-temperature substrate $T_b$, $P$ incident radiant power and $\eta$ its absorbed fraction. The model treats the element as having a single temperature and neglects changes in readout self-heating. A step to constant incident power $P_0$ givesThe thermal time constant therefore connects sensitivity to response speed. Lowering $G$ increases the steady temperature rise, but at fixed $C$ also lengthens the response.^[ref]

For an original example, choose $C=10^{-9}\mathrm{J}{\mathrm{K}}^{-1}$, $G=10^{-7}\mathrm{W}{\mathrm{K}}^{-1}$, $\eta =0.8$ and $P_0=1\mathrm{nW}$. Then $\tau =10\mathrm{ms}$ and the final sensing-element rise is $8\mathrm{mK}$; after $30\mathrm{ms}$ it has reached about $95\%$ of that rise. If the initial resistance is $100\mathrm{k\Omega }$ and the temperature coefficient of resistance is $\alpha =-0.02{\mathrm{K}}^{-1}$, the linear approximation $\Delta R\approx \alpha R\theta$ gives $\Delta R=-16\Omega$ at steady state. These stipulated values illustrate the model, not a particular camera's specification.

The sensing element's temperature rise is not the observed object's temperature rise. Inferring object temperature from the measured infrared signal additionally depends on emissivity, reflected radiation, the optical path and measurement calibration. “Uncooled” also permits temperature stabilization of the array; it describes the absence of required cryogenic operation, not the absence of thermal design.

A wirewound resistor uses a metal alloy chosen for stable electrical resistivity. Compared with a typical carbon composition resistor, it can offer tighter resistor tolerance, a smaller temperature coefficient of resistance, lower excess electrical noise, and greater continuous electrical dissipation when its construction provides an adequate heat path. These are design-dependent advantages, rather than guarantees for every alloy or package.

The winding has parasitic inductance and interturn capacitance. Its electrical impedance therefore ceases to be a nearly real electrical resistance at sufficiently high frequencies; an approximate model is a series circuit $R+i\omega L$ shunted by a small parasitic capacitance. A resonance can occur, making a wirewound resistor unsuitable where a nearly frequency-independent electrical resistance is required. Noninductive winding patterns reduce this problem. For comparable small-signal duties it is usually larger and more expensive. A carbon composition resistor is compact and has relatively small parasitic inductance, but commonly has poorer stability, larger resistor tolerance, and more excess electrical noise.

A reference resistor is a resistor whose assigned electrical resistance supplies the comparison value in a resistance-measurement circuit. Its value may come from measurement calibration rather than its nominal marking. The useful reference is its value under the stated temperature, loading and connection conditions, together with the associated measurement uncertainty.

In a shared-excitation resistance ratio measurement, the sensor and reference resistor carry the same electric current. Measuring their electric potential differences gives $r=V_T/V_{\mathrm{ref}}=R_T/R_{\mathrm{ref}}$, so $R_T=r{R}_{\mathrm{ref}}$. A reference value error therefore sets a scale error even when excitation cancels perfectly. Reference-resistor error in ratiometric resistance measurement derives the exact relation and distinguishes a correction from its remaining measurement uncertainty.^[ref]

The connections define which resistance is compared. In four-terminal sensing, two leads carry the electric current while a separate high-impedance pair senses the electric potential difference at the reference terminals. This avoids including the current-lead drops in the assigned reference value, within the sensing instrument's limitations.

For an original ideal example, a $100\Omega$ reference resistor carries $1\mathrm{mA}$ through two current leads, each of electrical resistance $0.20\Omega$. The reference element has a potential difference of $0.1000\mathrm{V}$, while a reading outside both leads is $0.1004\mathrm{V}$. If this latter reading is used as the denominator while the calculation assumes $100\Omega$, a true $50\Omega$ sensor is inferred asSensing directly at the reference terminals removes this idealized lead contribution. It does not correct a wrong reference value. The circuit guide explicitly shows a Kelvin connection at the reference terminals for this purpose.^[ref]

A small temperature change shifts the value approximately by $\Delta R_{\mathrm{ref}}/R_{\mathrm{ref}}\simeq {\alpha }_R\Delta T$, with temperature coefficient of resistance ${\alpha }_R$. Excitation also dissipates electric power $I^2{R}_{\mathrm{ref}}$; a reference with a different temperature or load from its measurement calibration may require a correction or additional measurement uncertainty. A proposed check compares the reference before and after the measurement sequence under the same connection and loading conditions. Repeating the comparison at a lower electric current tests for a heating contribution. Stability of the observed ratio alone cannot certify the reference's assigned value.

Reference-resistor error in ratiometric resistance measurement is the error left when an instrument converts a measured resistance ratio using an inaccurate value for its reference resistor. Shared excitation removes one nuisance input; it does not establish the denominator's true electrical resistance.

Let $R_a$ be the actual reference resistor value and $R_c$ the value used in calculation. For an ideal simultaneous reading $r=R_T/R_a$, the inferred sensor resistance isWriting $R_a=R_c(1+e)$ gives the exact fractional error $-e/(1+e)$. The familiar $-e$ is its first-order approximation. If a deterministic bound is $|e|\le E<1$, the inferred fractional error lies inA symmetric reference tolerance therefore produces a slightly asymmetric resistance-error interval.

For an original example, suppose the instrument uses $R_c=2000\Omega$ while the actual reference resistor is $2001.6\Omega$. A true $150\Omega$ sensor is reported as $149.880096\dots \Omega$, an error near $-0.07994\%$. Multiplying the shared excitation by any common positive number leaves this error unchanged in the ideal model. Using a measured and corrected $R_c$ instead of its nominal marking can remove the known part, while the corrected value retains its own measurement uncertainty.

Temperature variation can produce the remaining error after measurement calibration. Locally, $e(T)\simeq e(T_0)+{\alpha }_R(T-T_0)$, where ${\alpha }_R$ is the temperature coefficient of resistance. For example, a $20$-parts-per-million-per-kelvin coefficient over $15\mathrm{K}$ contributes roughly $300$ parts per million; it survives excitation cancellation. The primary circuit guide explicitly requires reference accuracy and low drift, and separates these requirements from shared-current cancellation.^[ref]

For small random errors, applying the law of propagation of uncertainty to ${\hat{R}}_T=r{R}_c$ givesThe covariance term must follow how the reference value and reading were obtained; it cannot simply be assumed zero when inputs are shared.^[ref]

Sensor self-heating in a ratiometric resistance measurement occurs when the sensing electric current changes the sensor's own temperature through Joule heating. A ratiometric measurement can remove the direct dependence of the electrical reading on that electric current while still reading the heated sensor correctly. For a resistance thermometer, that means the indicated temperature can differ from the unperturbed surroundings.

With actual sensor electrical resistance $R_T(I)$ and a stable reference resistor $R_{\mathrm{ref}}$ carrying the same electric current,The cancellation leaves the dependence of $R_T$ on $I$ intact. In a small, steady perturbation, a model with thermal resistance $R_{\mathrm{th}}$ gives $\Delta T\simeq R_{\mathrm{th}}{I}^2{R}_T(0)$ andwhere ${\alpha }_R$ is the temperature coefficient of resistance. These approximations require small heating and thermal conditions that remain comparable between readings. The BIPM guide distinguishes heat flow inside the probe from heat flow into its surroundings; changing the surrounding medium can change the effect.^[ref]

A practical diagnostic is a two-current extrapolation. Model $R_T(I)\simeq R_0+c{I}^2$ over the tested range. Measurements $R_1,R_2$ at distinct nonzero current magnitudes $I_1,I_2$ imply$R_0$ is an inferred zero-power electrical resistance, not an electrical reading taken with zero excitation. The guide describes this squared-current method and requires a stable surrounding temperature and settled readings.^[ref]

For an original numerical example, suppose a $1000\Omega$ reference resistor gives ratios $0.120006$ at $0.5\mathrm{mA}$ and $0.120024$ at $1.0\mathrm{mA}$. The inferred resistances are $120.006\Omega$ and $120.024\Omega$. Since $I_2^2=4I_1^2$, the estimate is $(4R_1-R_2)/3=120.000\Omega$. Both ratios canceled their excitation exactly, yet they disagree because the sensor changed.

A bath experiment should alternate the two excitation settings, allow thermal settling and monitor the bath temperature. Repeated low/high/low readings help reveal drift rather than attributing every difference to heating. Resistance thermometer self-heating gives the wider physical setting; reference-resistor error in ratiometric resistance measurement and mismatched filters are separate contributions.

A shunt resistor is a resistor used to establish a known relation between current and a measured electric potential difference. For current sensing, it is placed in the measured current path, and Ohm's law givesThe voltage-sensing circuit should draw negligible extra current for this simple relation to describe the desired branch current. Its small series voltage drop is often called the burden voltage.

An original example uses $R_s=10\mathrm{m\Omega }$ and $I=5\mathrm{A}$. The sensed drop is50millivolts and Joule heating dissipatesReducing resistance lowers both the burden and dissipation, but also reduces signal relative to a fixed amplifier offset or readout noise. The nominal resistor value alone therefore does not determine measurement quality.

Lead and contact resistance can dominate a low-value shunt. If a10milliohm shunt is inadvertently measured together with2milliohms of current-carrying interconnect, interpreting the total voltage using only the nominal shunt value overestimates current by20percent. Four-terminal sensing separates the high-current connections from the voltage-sense connections. Analog Devices' LTC6115 data sheet illustrates these Kelvin sense paths and explains how interconnect resistance introduces error.^[ref]

A practical characterization drives known currents through the shunt while measuring the voltage at its sense terminals, then repeats after thermal settling. Temperature coefficient of resistance, self-heating and connection geometry affect the realized conversion. The amplifier's operating range and measurement calibration must be assessed alongside the resistor.

A shunt converts current into a local voltage signal; it does not inherently provide electrical isolation between the measured circuit and its readout. High-side current sensing and low-side current sensing describe alternative placements of that measurement relative to the load and reference conductor.